Bar code detecting circuitry

ABSTRACT

A wide bandwidth slope detector has a comparator with first and second time constant circuits coupled to first and second inputs thereof. Where one time constant is on the order of three times the other, the comparator will change state in response to the slopes of an input analog signal coupled to the time constant circuit. Feedback can be provided by a fixed resistor or by a tracking circuit. A smoothing or clipping circuit can be used to pre-process the input analog signals to eliminate noise therefrom. A bar code reading system combines first and second clipping circuits to smooth the highs and lows of the input signal, coupled to a slope detector. The tracking circuit can be used to provide a symmetrical hysteresis characteristic.

FIELD OF THE INVENTION

The invention pertains to circuitry for detecting bar codes carried on amedium and for generating binary representations thereof. Moreparticularly, the invention pertains to circuits which smooth or clippeak values of a bar code modulated analog signal and which detectslopes therein.

BACKGROUND OF THE INVENTION

The use of bar codes to identify products, documents, or other media, orto specify characteristics thereof, has become very common. Bar codescan improve the speed and accuracy of information transfer.Unfortunately, the increase in bar code use has led to difficulties inread accuracy and reliability.

In known read systems, a source is usually used to generate a beam ofradiant energy which is directed onto the bar code, usually by moving abar coded medium through a read station. A photodetector is used todetect radiant energy reflected off of the moving bar code.

The photodetector produces a bar code modulated analog signal inresponse to reflected radiant energy. The modulated analog signal, whichcan have high and low amplitudes corresponding to the bar and spaceelements of the bar code, is then converted to a binary representationof the bar coded information.

FIG. 1 illustrates a medium M which carries a bar code B previouslyapplied thereto. The bar code B can be detected and converted to abinary representation thereof by means of a known read system 10.

The system 10 includes a source of radiant energy 12. The source 12 isused to generate a beam of radiant energy R_(I), which could bemonochromatic, and to direct that beam R_(I) onto a predetermined regionof a read area.

As the medium M and associated bar code B move in a direction 14 pastthe predefined region, the radiant energy R_(I) is reflected by theelements of the bar code B, thereby forming a modulated, reflected beamof radiant energy R_(F). The beam R_(F) is directed to a radiant energysensor 16. The sensor 16 could be a photodiode, for example, aphototransistor, or other photo-sensitive device.

Output from the sensor 16 on a conductor or a line 18 is a modulated,analog, electrical signal 20 which is representative of the elements ofthe bar code B. The analog signal 20 is coupled to a discriminatorcircuit 22. Known discriminator circuits include amplitude comparators,as well as various types of differentiators.

The output signal from the discriminator circuit 22 on a line 24, whichmight be, for example, a bi-valued voltage, +V and -V, is arepresentation of the modulated analog signal 26. The signal 26 could becoupled to a converter 28 for purposes of generating a digitizedrepresentation 30 of the modulated analog signal 20 at logic voltagelevels.

One problem associated with bar code reading circuitry is noise, whichcan cause false "ones" or "zeros" in the binary output stream. Noise canbe due to variations in the quality of the bar code, as well as theconfiguration of the read circuitry.

In many applications, inexpensive printers are used to create bar codeson surfaces with some degree of roughness. The printer may print barswith a significant degree of Element Reflectance Nonuniformity (ERN), asdefined in ANSI Standard X3.182-1990, or reflectance variation across anelement. Sensitive detectors may interpret the nonuniformity asadditional bar or space elements, thus misreading the code.

A granular surface onto which the codes are printed may contribute toERN by differentially reflecting more or less light onto the detector. Anonuniform absorption of the printing into the surface material can alsocontribute to ERN.

Another problem associated with known bar code reading circuits isinaccuracy caused by limited dynamic range of the read circuitry. As aresult, that circuitry is unable to discriminate relatively highfrequency bar coded elements. This in turn imposes limitations on thevelocity at which the bar coded medium M can move through the readstation, as well as the range of velocity variations of the medium Mthat can be tolerated by the read circuitry.

Often, the bar and space element speed is high enough that the detectorattenuates the amplitude of the narrow and higher frequency elementsrelative to the wide elements. This effect is defined as modulation inthe ANSI Specification X3.192-1990 "Bar Code Print Quality Guideline".

Modulation of the bar coded signal may occur when bandwidth-limitedsensors are employed in bar code readers. This effect leads to elementswith the same logical value, one or zero, but with differing amplitudesas the code is scanned.

Wide elements typically have a lower frequency content than do thenarrow elements, and thus, would possess higher amplitudes in thebandwidth limited systems. The convolution of an aperture and wide ornarrow bar code elements may also contribute to higher amplitudes forwide elements relative to narrow elements.

The rate at which the bar and space elements of a bar code symbol aresensed represents a set of frequencies to which the detector must beresponsive. As the elements are sensed at higher and higher speeds, thefrequency response requirements of the detector increases.

The ERN of the wide elements is detectable as signal changes within abar code element. The modulation effects are detectable as changes inamplitude between portions of the signal representative of the samelogical value. FIG. 2 is a graphical example of ERN and modulationpresent on the modulated analog signal 20 of FIG. 1.

In the waveform 20, the ERN noise 20a, while illustrated in connectionwith positive peak analog values, is also present on negative peakvalues. Similarly, the modulation effects reduce both positive peakvalues, such as 20b, and increases negative peak values (not shown.)

In addition to the effects of bandwidth-limited sensors, modulation of abar code may be created in other ways. For a given aperture size of asensor, there is a minimum element width which will generate a maximumsignal. Bar or space elements which are narrower than this minimum willallow reflected light from adjoining elements to "leak" onto thedetector, reducing the signal amplitude.

A third method by which signal modulation may occur is by tilting anon-symmetric (i.e., rectangular) aperture with respect to the bar andspace element edges. The combination of a tilted aperture across barcode element edges results in a reduced amplitude for narrow bars andspaces relative to wide bar and space amplitudes.

As seen in FIG. 2, the modulation need not be symmetrically placed withrespect to wide bars and spaces. Bar code edge detectors utilizingthreshold crossing or peak detection techniques are at times not capableof decoding signals with the modulation shown in FIG. 2 with the desiredaccuracy and reliability.

Circuits which differentiate the signal are theoretically capable ofidentifying each positive and negative peak where the first derivativeof the input signal goes to zero. Although the output of this type ofcircuit is independent of the absolute signal amplitude, adifferentiator is very sensitive to any high frequency noise which maybe present or the signal. Hence, ERN noise can produce false "one" or"zero" pulses.

Additionally, modulation effects can modify the sensor waveform to thepoint that traditional element edge determination techniques do notfunction adequately.

The use of hysteresis produced by positive feedback in comparatorcircuits may also limit the dynamic range of bar code speeds. Largeamounts of positive feedback will tend to limit the ability of a systemto detect low amplitude signals, such as those generated by lowbandwidth systems when exposed to high speed bar codes. At very low barcode speeds, where an unchanging input signal exists for a significantamount of time, the low hysteresis levels needed for high speedoperation may not be adequate in the presence of electronic noise andthe input offset voltage inherent in comparators.

Therefore, a bar code digitizing circuit must reconcile severalconflicting performance requirements in order to accurately and reliablyinterpret an incoming waveform. This waveform may consist of high or lowfrequency constituents, ERN, modulation, overall amplitude variations,acceleration, or other undesirable modifiers to the bar coded signal.

Thus, there continues to be a need for accurate, noise insensitive readcircuity with substantial bandwidth. Preferably, such circuitry will beinexpensive and readily manufacturable.

SUMMARY OF THE INVENTION

An amplitude independent slope detector is provided in accordance withone aspect of the invention. The detector produces a binary outputsignal corresponding to an information sequence carried by an appliedanalog signal. The analog signal has varying peak amplitudes which arebounded by first and second slopes. Some of the amplitudes may besubstantially constant between respective slopes.

The detector includes a first circuit, to which the analog signal can becoupled, for detecting first and second slopes. The first circuit can beimplemented with first and second RC time constant circuits. In apreferred embodiment, one of the time constants is on the order of threetimes the other time constant.

A second circuit is coupled to the first circuit. The second circuit isresponsive only to the detected slopes.

The second circuit produces first and second binary output values,corresponding to the information sequence carried by the input analogsignal. Each of the output values is initiated when a respective one ofthe slopes is detected and is maintained at that value in the presenceof a substantially zero slope, a substantially constant amplitude, untilthe other slope is detected. When the other slope is detected, the otheroutput value is initiated.

The second circuit can be implemented with an electronic comparator,such as an integrated circuit voltage comparator. A resistive feedbackelement can be coupled between the output of the comparator and one ofthe time constant circuits for improved stability.

In another aspect of the invention, the feedback resistor can bereplaced with a tracking and decoupling circuit to provide symmetrichysteresis for the slope detector circuit. The tracking circuit includesan operational amplifier to track the input signal and to adjust thehysteresis symmetrically with respect to that input signal. In thisconfiguration, neither the positive nor the negative hysteresis valueswill be influenced by changes in the output signal of the operationalamplifier.

In yet another aspect of the invention, a circuit is provided forsmoothing or minimizing noise present in peak values of an analog inputsignal. The apparatus includes circuitry for sensing the input analogsignal.

The sensing circuitry is coupled to circuitry for clipping orsubstituting non-noisy peak amplitude values for the noise carrying peakamplitude values. As a result, a substantially noise-free representationof the input analog signal can be formed.

In yet another aspect of the invention, the clipping circuitry caninclude a peak detector circuit, which is coupled to a peak holdcircuit. An output switching circuit is coupled to the peak holdcircuit, as well as an amplified representation of the input analogsignal. The output of the circuit is a smoothed analog output waveformfrom which the noise has been removed from the peak amplitudes.

In yet another aspect of the invention, a system is provided forconverting an analog input signal having varying peak values andtransitions to a binary output signal indicative of the transitions. Thecircuit includes at least one analog smoothing or clipping circuit,which processes and eliminates noise in the peak values of the appliedanalog input signal.

The smoothing or clipping circuit is coupled to a slope detectingcircuit which detects transitions in the smoothed input signal. Theslope detecting circuit then generates binary output signals in responseto the detected transitions.

A second clipping circuit can be used to smooth both high or low peakvalues of the modulated input signal. Preferably, the slope detectingcircuit will include a tracking circuit to provide a symmetricalhysteresis characteristic.

A system in accordance with the present invention can accurately convertan input analog signal to a binary signal over a wide dynamic range. Thesystem also reliably operates in the presence of relatively long,substantially constant, peak values of the input analog signal.

Alternately, digital techniques can be used to process the modulatedanalog input signal. One or more digital signal processors can be usedto implement this embodiment.

These and other aspects and attributes of the present invention will bediscussed with reference to the following drawings and accompanyingspecification.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 is a block diagram of known bar code read circuitry;

FIG. 2 is a graph of modulated analog voltage for the circuitry of FIG.1 as a function of time;

FIG. 3 is a block diagram of a clipping circuit in accordance with thepresent invention;

FIG. 4 is a graph of an input and internal signals for a positiveclipping circuit as illustrated in FIG. 3 as a function of time;

FIG. 5 is graph of the output of a positive clipping circuit inaccordance with FIG. 3, in response to the input signal of FIG. 4 as afunction of time;

FIG. 6 is a graph of an input and internal signals for a negativeclipping circuit as in FIG. 3 as a function of time;

FIG. 7 is a graph of the output of a negative clipping circuit inaccordance with FIG. 3, in response to the input signal of FIG. 6 as afunction of time;

FIG. 8 is a schematic of the circuit of FIG. 3 configured to clip andsmooth positive peak values of an input signal;

FIG. 9 is a schematic diagram of the circuit of FIG. 3 configured toclip and smooth negative peak values of an input signal;

FIG. 10 is a schematic diagram of a slope detector in accordance withthe present invention;

FIG. 11 is a graph of input and output waveforms of the detector of FIG.10 as a function of time;

FIG. 12 is a schematic of an improved slope detector in accordance withthe present invention;

FIG. 13 is a block diagram of a bar code digitizing system in accordancewith the present invention;

FIG. 14 is a schematic diagram of the digitizing system of FIG. 13;

FIG. 15 is a graph of various signals of the circuit of FIG. 14 as afunction of time; and

FIG. 16 is a block diagram of an alternate digital embodiment inaccordance with the present invention.

DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENT

While this invention is susceptible of embodiment in many differentforms, there is shown in the drawing, and will be described herein indetail, specific embodiments thereof with the understanding that thepresent disclosure is to be considered as an exemplification of theprinciples of the invention and is not intended to limit the inventionto the specific embodiments illustrated.

A noise suppression or clipping circuit 40, in accordance with thepresent invention, is illustrated in the block diagram of FIG. 3. Thecircuit 40 is coupled to the sensor 16 and receives a noisy informationmodulated signal, corresponding to the signal 20 of FIG. 2, on theconductor or line 18.

The signal 20 is coupled to an attenuator 42 and an amplifier 44. Outputfrom the attenuator 42 is coupled to a peak detector 46 and peak holdcircuity 48.

Outputs 44a, 48a from the amplifier 44 and the peak hold circuit 48 arecoupled via conductors or lines 44b, 48b to a voltage limiter circuit50. The output from the limiter circuit 50, on a line 50b, is anon-noisy analog signal, representative of the noisy input signal 20.

The peak hold circuitry 48 includes an RC time constant to sense andhold the maximum positive excursion of the input signal 20. In addition,the input signal 20 is amplified by the amplifier 44, an amount thatcauses all of the ERN negative going excursions to be at a highervoltage than the voltage at the output of the peak hold circuit 48.

Only the lower voltage signal of the peak hold circuit 48, on the line48b, or the output of the amplifier 44, on the line 44b, is output fromthe limiter 50, on the line 50b. Hence, the ERN noise can be eliminatedfrom the output signal 50a.

Thus, when a wide, large amplitude element with ERN noise is beingdetected, the peak detector 46 and peak hold circuit 48 produces theoutput. When the bar code sensor senses lower amplitude elements withoutthe ERN noise, the amplified signal from the amplifier 44 becomes theoutput.

ERN noise can be eliminated for positive or negative peak values, suchas 20a, using the circuit 40. The attenuator 42 may not be needed for anegative peak clipping or smoothing circuit.

FIG. 4 is a graph illustrating various signals for the circuit of FIG. 3configured to smooth positive peak input values for the signal 20. FIG.5 illustrates the smoothed output 51p from the circuit 40 when soconfigured.

FIGS. 6 and 7 illustrate waveforms associated with the smoothing circuit40 when configured to clip and smooth negative peak values of themodulated analog signal 20. The output signal 51n of FIG. 7 has smoothednegative peak values.

For voltage signals from the sensor 16 which are positive, theattenuator circuit 42 and amplifier 44 have opposite effects. Theattenuator 42 reduces the waveform amplitude and the amplifier 44increases the amplitude.

For signals from the sensor 16 which are negative, the attenuatorcircuit 42 and amplifier circuit 44 act in the same direction, movingthe waveform towards a negative voltage reference. In this case, it maybe necessary to attenuate the signal more than the amplification of thenegative voltage.

For either positive or negative peak signals, the proper combination ofattenuation and amplification is one where the lowest expected ERNvoltage amplitude in the amplified signal is greater than the largestvoltage amplitude in the attenuated signals for a bar code element. Whenthe output of the positive peak detector and hold circuits 46 and 48 andthe output of the amplifier 44 are connected to the voltage limitercircuit 50, the output on the line 50b is the lower voltage amplitude ofthe two inputs.

FIG. 8 illustrates positive peak clipping circuitry 40a by which theunwanted ERN or positive peak values of the incoming signal 20 iseliminated. The signal from an optical sensor 16 is input to theattenuator 42, formed of resistors 60a, and 60b. The amplitude of thesignal 20 is reduced by the ratio of resistor 60a to the sum ofresistors 60a and 60b.

If the sensor voltage waveform is positive, the negative voltagereference -V_(r) is set to ground potential. If the sensor waveform isnegative, the voltage reference -V_(r) is a fixed negative voltage oflower potential than the sensor waveform.

The attenuated signal enters the peak detector circuit 46p. The positivepeak detector 46p includes an operational amplifier 62a, diodes 62b,62c, and an input resistor 62d.

Diode 62b limits the output of amplifier 62a to voltages higher thanthat stored at the input of the peak hold circuit 48p. The diode 62climits the output of the amplifier 62a to a maximum of one diode forwardvoltage drop from the stored voltage on the input to the peak holdcircuit 48p.

The positive peak hold circuit 48p contains a storage capacitor 64a anda resistor 64b referenced to -V_(r). A time constant formed by thecapacitor 64a and resistor 64b allows a slow decay in voltage towards-V_(r) relative to the rate at which bar and space elements are sensed.

Thus, if the overall signal level changes as a bar code is scanned dueto reflectance or other optical variations, the peak hold circuitry 48pcan reestablish the relative peak voltage based on recent signal levels.Otherwise, the peak hold circuit 48p is fixed at the highest voltagesensed by the peak detector circuit 46p. Any ERN voltage in the incomingwaveform 20 does not change the output of the peak hold circuit 48p.

Amplifiers 66a and 68a, along with resistors 66b and 66c, and 68b and68c, respectively, buffer the signal from loading by other circuitelements.

The output of the peak detector and hold circuits 46p, 48p is themaximum voltage of the attenuated output signal, slowly decaying inamplitude based on the RC time constant formed of resistor 64b andcapacitor 64a. As soon as the attenuated input signal amplitude risesabove the voltage on the capacitor 64a, the output of amplifier 62aquickly increases the voltage on that capacitor to be equal to theamplifier input. The output of the peak detector and peak hold circuitson a line 49p thus rises quickly and falls slowly.

The sensor waveform on the line 18 is also input to amplifier circuit44. The amplifier circuit 44 includes an operational amplifier 70a,input resistor 70b, and feedback resistors 70c, 70d. It is the properselection of attenuation in the circuit 42 and amplification in thecircuit 44 which suppresses the unwanted ERN voltage. The gain of thiscircuit is equal to one plus the ratio of the resistor 70c to theresistor 70d.

With the undesirable ERN eliminated, a differentiator or other circuitrycan be employed to determine bar and space edges. This edgedetermination process can convert the waveform into digital levels as afunction of time for subsequent decoding.

FIG. 9 is a schematic of a negative peak clipping and smoothing circuit40b by which the unwanted ERN on negative peak values of the incomingsignal can be eliminated. Because of changes in the connectivity of thenegative peak detector 46n and negative peak hold circuit 48n, theattenuator 42 can be eliminated from the negative peak smoothing circuit40b.

The signal from an optical sensor 16 is input to the negative peakdetector circuit 46n. That circuit includes an amplifier 82a, an outputdiode 82b, feedback diode and resistor 82c, 82d, and an input resistor82e.

The diode 82b restricts the amplifier 82a to outputting only voltageslower than that on the input of the peak hold circuit 48n. Diode 82cmaintains the output of amplifier 82a a maximum of one diode forwardvoltage drop from the voltage on the input to the negative peak holdcircuit 48n.

The negative peak hold circuit 48n includes an input RC time constantcircuit, with capacitor 84a, and resistor 84b, coupled to an operationalamplifier 86a through an input resistor 86b. The resistor 86c provides afeedback path and the resistor 86d provides a negative input for theoperational amplifier 86a.

Output from the amplifier 86a is coupled to a buffer output amplifier88a via an input resistor 88b. A feedback resistor 88c is coupledbetween the output 48n and the inverted input of the amplifier 88a. Thecapacitor 84a and resistor 84b are coupled to a positive voltage +V_(r).

If the incoming waveform is negative +V_(r) is set to ground potential.For positive voltage waveforms, +V_(r) is set to a level which is higherthan the highest expected voltage of any negative excursion of theincoming signal plus the ERN.

The time constant formed by the capacitor 84a and resistor 84b allows aslow decay in voltage towards the +V_(r) relative to the rate at whichbar and space elements are sensed. Thus, if the overall input signallevel changes as a bar code is scanned due to reflectance or otheroptical variations, the peak hold circuity 48n can reestablish therelative peak voltage based on recent signal levels. Otherwise, the peakhold circuit is fixed at the lowest voltage sensed by the negative peakdetector circuit 46n. Any ERN voltage in the incoming waveform does notchange the output of the peak hold circuit 48n.

The peak detector circuit 46n and the peak hold circuit 48n togetherprovide an overall gain factor for the input signal. When the circuitsare configured such that if the ratio of resistor 82e to resistor 82d isequal to the ratio of resistor 86c to resistor 86d, the gain of the twocircuits is equal to: ##EQU1##

The voltage follower, amplifier 88a, and resistors 88b and 88c,respectively, buffer the stored peak signal from loading by othercircuit elements.

The output of the negative peak hold circuit 48n is the value of theminimum voltage of the input signal times the gain. This value slowlyrises in amplitude towards +V_(r) based on the time constant ofcapacitor 84a and resistor 84b.

As soon as the input signal amplitude drops below the stored voltage onthe capacitor 84a, the output of amplifier 82a quickly restores thevoltage on the capacitor 84a to be equal to the amplified input. As aresult, the output of the negative peak hold circuit 48n falls quicklyand rises slowly.

In addition to the negative peak detector and hold circuits 46n, 48n,the sensor waveform is input to the amplifier circuit 44. The properselection of amplification in circuit 44 relative to the amplificationformed by circuits 46n and 48n, suppresses the unwanted ERN voltage. Thegain of the circuit is equal to one plus the ratio of the resistor 70cto the resistor 70d.

For either positive or negative signals, the proper amplification levelsare where the highest expect ERN voltage in the amplified signal fromcircuit 44 is lower than the lowest voltage produced by circuits 46n and48n.

The output of the negative peak detector 46n and hold circuits 48n, andthe output of the amplifier 44 are connected to the voltage limitercircuit 50n. The voltage limiter circuit 50n includes a resistor 92a anda diode 92b. The output of the limiter 50n on the line 51n is the highervoltage of the two input lines 44n and 49n.

FIG. 6 illustrates the output on the line 49n of the negative peakdetector and hold circuitry 46n, 48n, and the output on the line 44n ofthe amplifier 44 in relation to the sensor input waveform. FIG. 7illustrates how the voltage limiter circuit 50n alternately chooseswhich of the two inputs drives the output signal on the line 51n,depending upon the relative magnitudes.

Subsequent to removing, ERN noise using the smoothing circuits of FIGS.8 and 9, a determination must be made as to which portions of thesmoothed signal should be represented as binary "one" or binary "zero"value. This determination preferably will be made using an edge detector100, in accordance with the present invention, as illustrated in FIG.10.

The detector 100 can be used to detect bar code elements moving over awide range of velocities and is insensitive to modulation and smallamplitude, high frequency noise. A comparator 102 and first and secondRC circuits 104a, 104b are configured such that the output of thedetector 100 is determined by the sign of the difference of the firstderivative of the voltage signals at inputs 102a, 102b to the comparator102.

This arrangement incorporates the advantage of absolute amplitudeinsensitivity without the excessive noise sensitivity of adifferentiator circuit. The output of the detector 100 on a line 102c isone of two discrete voltage values which, if not already digital 5 voltsand 0 volts, can easily be converted into such.

The detector 100 has an input line 104c coupled to the circuits 104a,104b. The circuit 104a includes a resistor 106a and a capacitor 106b.The circuit 104b includes a resistor 108a and a capacitor 108b.

The output voltage 1/0 on the line 102c is given by:

    V.sub.0 =A sgn(V+-V-)                                      (1)

Where:

A= The amplitude of the output signal

V+= The voltage at the positive input 102a of the comparator 102

V-= The voltage at the negative input 102b of the comparator 102

sgn(x)= sign function of x,

sgn(x)=1, x≧0

sgn(x)=-1, x<0

Then:

    V.sub.0 =A sgn[τ104b*(V-)'-τ104a*(V+)']            (2)

Where:

(V+)'= The first derivative with respect to time of the input voltagesignal V+

(V-)'= The first derivative with respect to time of the input voltagesignal V-

τ104a=R106a*C106b

τ104b=R108a*C108b

A feedback resistor 109 is used to create a small amount of hysteresisin the detector 100. This feedback increases circuit stability in thepresence of electrical noise. Consequently, the resistance value R109 ofthe resistor 109 is generally much greater than the resistance valueR106a of the input resistor 106a (2 or 3 orders of magnitude, forexample).

Proper bar code element detection is achieved by the detector 100 whenthe RC time constant τ104a formed by the resistor 106a and capacitor106b, is smaller than the RC time constant τ104b formed by the resistor108a and the capacitor 108b. With this arrangement, the voltage signalon the capacitor 106b will phase lead the signal on the capacitor 108b.

When the sensor 16 scans an element (bar or space), the voltage signalinput on the line 104c will peak high or low. The input signal then movefrom that peak value towards an opposite peak.

As the signal peaks, (V+)' at the input 102a will change sign before(V-)' at the input 102b. Since the time constant τ104a is less than thetime constant τ104b, the output V₀ on the line 102c will not changesign, which determines the element edge, until (V-)' is reduced inamplitude such that: ##EQU2##

For example, if τ104b=3*τ104a, then the output V₀ of the comparator 102will not change its output until (V+)'>3*(V-)'.

The selection of the ratio between τ104a and τ104b is a trade-offbetween increased sensitivity to bar and space peaks, and immunity fromunwanted transitions caused by noise. As the ratio increases, (V+)' mustbe larger and larger than (V-)' in order to change the comparatoroutput. In this manner, the excess sensitivity to high frequency noise,characteristic of differentiator circuits, is avoided.

Because equation 2 does not contain any terms relative to the signalamplitude, the detector 100 is insensitive to the effects of modulation.Only the derivative input signals (V+)' and (V-)' determine the outputV₀.

The positive feedback formed by the inclusion of resistor 109 acts tosuppress unwanted output changes caused by noise, or oscillation of thecomparator. The amount of hysteresis is determined by resistors 106a and109. The hysteresis voltage is given by:

    Hysteresis Voltage =[R106a/(R106a+R109]*V.sub.0

The hysteresis voltage serves to assure that when τ104a, (V+)'approaches τ104b, (V-)', only one transition of V₀ (as opposed toseveral, which can be caused by the influence of noise) occurs.

If the signal 20, illustrated in FIG. 1, is input into the slopedetector 100, the comparator 102 will switch state each time the signfunction in equation 2 changes from +1 to -1, or vice versa. FIG. 11illustrates this process as a function of time for a non-noisy inputsignal.

As noted previously in FIG. 10, hysteresis is provided in the detector100 by connecting resistor 109 between the output 102c comparator 102and the positive input 102a. However, this arrangement may result in anon-symmetrical hysteresis condition.

If the amplitude of the positive output voltage of the comparator 102 isnot equal to the amplitude of the negative output voltage, thehysteresis will not be symmetric with respect to the signal level V₀. Agreater positive feedback voltage must be overcome in order to changethe output in one direction than is required to change in the otherdirection.

The asymmetric hysteresis condition mentioned above may limit theoperation of the slope detector circuit 100. For example, if the smallerof the two hysteresis voltages is scaled for the expected inputwaveform, some small bar or space features may not generate a (V+)' or(V-)' large enough to cause a state change in the comparator 102.

If the larger of the hysteresis voltages is chosen for scaling, thereduced noise immunity of the smaller hysteresis may result in unwantedoutput changes and bar code misreads. In either case, the reducedsensitivity or lower noise immunity can result in lower performance ofthe detector 100.

Another limitation to the operation of the slope detector 100 is thatmost comparators have open-collector outputs. A resistor, connectedbetween the comparator output and a positive voltage source, pulls thesignal to its "high" level. If there are amplitude changes in thepositive voltage source due to current loading by another device sharingthe source, noise generated by or conducted into the voltage source (orother phenomena), V₀ variation results in changes in hysteresis voltage.

As a result, it may be necessary to increase the hysteresis amplitude byan amount which anticipates these events. Once again, this may result inlarger than necessary positive feedback for the detector.

Therefore, the asymmetrical voltages and the V₀ amplitude sensitivityserve to limit the performance of the slope detector 100 in somecircumstances. To improve circuit performance, a tracking hysteresiscircuit can be used instead of the resistor 108.

FIG. 12 illustrates another circuit 10a with a feedback circuit 109a,which provides a symmetric hysteresis characteristic and is sensitive tocomparator output amplitudes. The detector 100 as described above isincorporated into the circuit 100a of FIG. 12. The feedback amplifiercircuit 109a tracks the input signal on the line 104e and to regulatethe hysteresis symmetrically with respect thereto. In this manner, thepositive and negative hysteresis values will be equal, and will not beinfluenced by changes in V₀.

The circuit 109a includes an operational amplifier 120, resistors 122aand 122b, diodes 124a and 124b, and resistors 126a and 126b. Theoperational amplifier 120 has been configured as a buffer, with theoutput of the device on a line 120a equal to the voltage at its positiveinput terminal 120b. The input 120b is connected to the input signal onthe line 104c through the input resistor 122a. The diodes 124a and 124bclamp the voltage at node 124c to a value equal to the input signal ±one diode forward voltage drop (i.e., about 0.7 volts).

The comparator 102 is configured such that its output voltage V₀ on theline 102c is higher than the input signal on the line 104c for V₀ ="high" and lower than the input signal for V₀ = "low". If the output V₀on the line 102c is at a high voltage, current will flow from thecomparator 102 through resistor 126b and diode 124b into the input 120cof the amplifier 120. Since the amplifier output on the line 120a is setat the input signal level, the voltage at the node 124c will be set tothe voltage at the input on the line 104c plus the forward voltage dropof the diode 124b.

If the comparator output on the line 102c is at a low voltage, currentflows from amplifier 120 through diode 124a and resistor 126a into thecomparator 102. This arrangement sets the voltage at the node 124c to avalue equal to the input signal level minus the forward voltage drop ofthe diode 124a.

As in the original slope detector 100, the output of the comparator ofthe detector 100a is given by equation 1. If the current flow into theinputs of the comparator 102 is negligible, and the output voltage V₀for the detector 100a can be expressed as: ##EQU3##

The hysteresis voltage ##EQU4## is no longer a function of V₀. It isdetermined by the ratio of resistors R106a and R126a, and the forwardvoltage drop V_(o) of the respective diode 124a or 124b. The hysteresisvoltage amplitude is thus independent of whether the output V₀ is "high"or "low".

This symmetric hysteresis characteristic permits a choice of the ratioof resistors which, when multiplied by the diode forward voltage dropV_(D), is large enough to suppress unwanted transitions. This value isstill small enough to allow small but valid changes in (V+)' and (V-)'to be sensed as bar and space elements, thereby increasing theperformance range of the detector 100a over that of the detector 100.

Like the slope detector 100 described above, the output V₀ of thedetector 100a is not a function of the input signal level, but of thefirst derivative of the voltages on the inputs 102a, 102b of thecomparator 102. Thus, the advantages of the insensitivity to modulationor amplitude variation are preserved in the detector 100a.

The previously discussed modules can be combined to form an improved barcode digitizing system 140, in accordance with the present invention.The system 140, as described subsequently, can detect and properlydigitize high and low speed bar coded signals that have been convertedto a modulated analog voltage, such as the voltage 20 of FIG. 2.

The circuit 140, with reference to FIG. 13, includes positive andnegative peak clipping circuits 142, 144, which are similar structurallyand functionally to the positive and negative peak smoothing circuits40a and 40b of FIGS. 8 and 9. In the system 140, the clippers 142, 144share a common gain stage 44. As described previously, the clippercircuits 142, 144, in combination with the gain stage 44, flatten theERN voltage, such as the ERN voltage 20a of FIG. 2, thereby forming acomposite, processed representation 21 of the input modulated analogsignal 20.

The processed analog signal 21, illustrated in FIG. 15, on a line 21a,is then input to a slope detector circuit 100b, similar to the detector100a. The output signal V₀ from the detector 100b can then betranslated, if needed, to logic levels in a translator or shiftercircuit 146 to produce a binary output signal V_(out).

FIG. 14 is a schematic of the system 140. In FIG. 14, elements whichwere previously described in connection with FIGS. 8, 9, and 12 havebeen given the same identification numerals, and need not be discussedfurther.

With respect to FIG. 14, the input signal 20 from the bar code sensor 16is input into the three subcircuits, the positive peak clipper 142, thenegative peak clipper 144, and the gain amplifier 44. As previouslydescribed with respect to FIGS. 8 and 9, the positive peak clipperattenuator, formed by resistors 60a and 60b, and the gain of thenegative peak clipper 144, are matched to the gain in circuit 44 suchthat all the ERN on the highest and lowest amplitude elements, such as20a, is higher or lower than the respective peak levels of the inputsignal 20.

The peak clipping circuits 142, 144, as previously discussed, do notaffect modulation per se, but smooth or flatten the tops and bottoms ofthe highest and lowest amplitude elements. FIG. 15 illustrates theeffects of conditioning the input signal 20 of FIG. 1 with the positiveand negative peak clipping circuits 142, 144, thereby producing aprocessed noise-free representation 21 thereof.

It is signals such as 21, shown in FIG. 15, which are input into theslope detector circuit 100b. A modification to the circuit 100a,described in FIG. 12, has been made in order to extend the performanceof the system.

Resistors 150a and 150b have been added to the slope detecting circuit100b of FIG. 14. The output of the detector 100b is given by equation 1.

For proper operation, the value of resistor 126a must be greater thanthe value of resistor 150a, such that: ##EQU5##

There are two cases to consider. When the output of the gain stage 44 ishigher than the positive peak clipper voltage output, or lower than thenegative peak clipper output, the active peak clipper voltageestablishes the input at resistor 108a. When the gain circuit 44 voltageis between the two peak levels, the gain output sets the voltage for thenegative input to the slope detector 100b. Case A will refer to thecircumstance where circuit 44 sets the voltage; and Case B will refer tothe case where a peak clipper circuit output sets the slope detectorinput level.

The output of the slope detector 100b is: ##EQU6##

Cases A and B represent the expected behavior for the circuit 140. Theterm ##EQU7## is small, but has been retained since it represents thehysteresis voltage on the slope detector. V_(PC) is the voltage level ofthe active peak clipper circuit and V_(g) is the voltage output from thegain circuit 44. The system accurately decodes a high or low speed,distorted signal as is described below.

With the use of slope detection to discriminate bars and spaces, thecircuit is insensitive to the absolute signal amplitude, or changes inthe amplitude across the bar code. Modulation of the signal or overallamplitude changes across the code occur in the waveform where the Case Bequation applies. Case B has no terms which are dependent upon the inputsignal amplitude. Only first derivative (slope) terms determine the signof the output V₀.

The positive feedback term of (±V_(d) R106a/R126a) is small in magnitudeso that low amplitude bar and space edges can generate a (V+)' and (V-)'large enough to change the sign of V₀. The small amount of hysteresis issufficient to keep the comparator 102 from oscillating at those pointsin a time when (V+)' and (V-)' are very close in magnitude.

There is a circumstance where (V+)' and (V-)' become very close to zero.That is when a wide element is being scanned such that the constantvoltage of a clipped bar or space element drives (V+)' and (V-)' down inmagnitude. This is Case A, defined earlier.

If Case A is examined, there is an extra voltage term which acts asadditional hysteresis to the small positive feedback. The term (V_(pc)-V_(g)) serves to increase the potential difference between the positiveand negative inputs to the comparator 102 at the same time that (V+)'and (V-)' become very small. This difference adds to the positivefeedback to protect the system from small voltage variations such asinput offset voltage, electronic noise, vibration induced signaltransients, or other phenomena which may be present.

During the scan of a bar code element where one of the peak clippersflattens the signal, the (V_(pc) -V_(g)) term increases the effectivenoise suppression. When the input signal falls below the peak value,this extra term disappears, allowing small amplitude elements to bedetectable.

Thus, the slope detector 100b can detect high speed, highly modulatedbar code elements. It can also properly decode very slow, very flatwaveform elements.

The tracking hysteresis circuit 109a requires that the output levels ofthe slope detector 100b be higher than the highest input voltage fromthe sensor 16, and lower than the lowest input voltage therefrom. Thatoften means that the slope detector output levels are not digitalcommonly used +5 volt and zero volt voltages.

Translator circuit 146 can be used to make a voltage conversion. Circuit146 includes a comparator 160, resistors 162 through 168, and schottkydiode 170. The circuit 146 can be used to convert the output levels V₀of the slope detector into digital one and digital zero voltages,corresponding to the binary output voltage V_(out) of FIG. 15.

Alternately, improved tracking can be achieved in the system 140 by opencircuiting a region 18a of the conductor 18, as illustrated in FIG. 14.In this instance, a connection 18b, illustrated in phantom in FIG. 14,is provided between the resistor 60a and the output line 21a.

In connection with the previously discussed circuits, comparators can beintegrated voltage comparators, type LM339AM. Operational amplifiers canbe LM324AM-type integrated circuits.

It will also be understood that the present invention includes alternateprocessing techniques. For example and without limitation, the output 20from the sensor 16 could be digitally processed in digital processingchips.

FIG. 16 is a block diagram of a digital system 190 in accordance withthe present invention. The digital system 190 digitizes the outputsignal 20 from the sensor 16 in an analog-to-digital converter 192. Thedigital values, on a line or lines 194, are coupled to one or moredigital signal processing chips 196.

The chips are configured to digitally process the input signal 20 inaccordance with the above described techniques. The output from thesignal processor 196, on a line 198, is a digitized representation ofthe modulated analog input signal 20. The output on the line 198corresponds to the output V_(out) on the line 172 of FIG. 14, but isachieved by digital rather than analog processing.

From the foregoing, it will be observed that numerous variations andmodifications may be effected without departing from the spirit andscope of the invention. It is to be understood that no limitation withrespect to the specific apparatus illustrated herein is intended orshould be inferred. It is, of course, intended to cover by the appendedclaims all such modifications as fall within the scope of the claims.

What is claimed is:
 1. An amplitude independent slope detector forproducing a binary output signal corresponding to a binary informationsequence carried by an analog signal having varying peak amplitudesbounded by first and second slopes, wherein at least some of theamplitudes are substantially constant between respective slopes, thedetector comprising:an input node to which the analog signal can becoupled, and an output node; a first, passive circuit, coupled to saidinput node, for detecting first and second slopes; a second circuit,coupled to said first circuit and said output node and responsive onlyto said detected slopes, for producing first and second binary outputvalues at said output node, wherein each said output value is initiatedwhen a respective one of said slopes is detected and maintained at saidvalue in the presence of a substantially constant amplitude until theother of said slopes is detected.
 2. An amplitude independent slopedetector for producing a binary output signal corresponding to a binaryinformation sequence carried by an analog signal having varying peakamplitudes bounded by first and second slopes, wherein at least some ofthe amplitudes are substantially constant between respective slopes, thedetector comprising:an input node to which the analog signal can becoupled, and an output node; a first circuit, coupled to said inputnode, for detecting first and second slopes;. a second circuit, coupledto said first circuit and said output node and responsive only to saiddetected slopes for producing first and second binary output values atsaid output node, wherein each said output value is initiated when arespective one of said slopes is detected and maintained at said valuein the presence of a substantially constant amplitude until the other ofsaid slopes is detected; and wherein said first circuit includes firstand second time constant circuits and wherein each said time constantcircuit includes a resistive input coupled to said input node.
 3. Anamplitude independent slope detector for producing a binary outputsignal corresponding to a binary information sequence carried by ananalog signal having varying peak amplitudes bounded by first and secondslopes, wherein at least some of the amplitudes are substantiallyconstant between respective slopes, the detector comprising:an inputnode to which the analog signal can be coupled, and an output node; afirst circuit, coupled to said input node, for detecting first andsecond slopes; a second circuit, coupled to said first circuit and saidoutput node and responsive only to said detected slopes for producingfirst and second binary output values at said output node, wherein eachsaid output value is initiated when a respective one of said slopes isdetected and maintained at said value in the presence of a substantiallyconstant amplitude until the other of said slopes is detected; andwherein said first circuit includes a first time constant means with afirst parameter value, and a second time constant means with a secondparameter value, and wherein said first value is on the order of threetimes greater than said second value.
 4. A detector as in claim 3wherein each said time constant means includes a resistor coupled to acapacitor.
 5. A detector as in claim 3 wherein each said time constantmeans includes a resistive input coupled to said input node.
 6. Adetector as in claim 1 wherein said second circuit includes acomparator.
 7. A detector as in claim 6 wherein said amplifier has firstand second inputs, each of which is coupled to said first circuit, andan output, which is coupled to said output node.
 8. A detector as inclaim 6 which includes hysteresis circuitry coupled between said outputnode and said first circuit.
 9. A detector as in claim 8 wherein saidhysteresis circuitry includes at least one resistor coupled between saidoutput node and said first circuit.
 10. A detector as in claim 8 whereinsaid hysteresis circuitry includes means for generating first and secondsubstantially equal hysteresis values.
 11. A detector as in claim 10wherein said generating means includes a decoupling circuit between saidoutput node and said first circuit.
 12. A detector as in claim 1 whereinsaid second circuit includes digital signal processing circuitry.
 13. Aslope responsive circuit, usable with an input signal having at leasttwo different amplitudes, for detecting at least first and second slopesas the input signal changes direction, and for producing a binary outputsignal representative of the amplitudes, comprising:circuit means fordetecting at least first and second non-zero slopes as in the inputsignal changes direction; and analog circuit means, responsive to eachsaid detected non-zero slope, for generating a binary output signal of aselected value associated with each said detected slope, including meansfor subsequently maintaining said binary output signal at said selectedvalue until another of said non-zero slopes is detected and wherein saiddetecting means includes a first circuit for forming a first timeconstant value and a second circuit for forming a second time constantvalue, wherein said time constant values are different.
 14. A circuit asin claim 13 wherein said first and second circuits each include acapacitor.
 15. A circuit as in claim 13 wherein said analog circuitmeans includes a comparator.
 16. A circuit as in claim 13 including atracking hysteresis circuit coupled to said analog circuit means.
 17. Aslope-responsive, amplitude independent method of detecting informationcarried by an analog signal having at least some peak amplitudes ofsubstantially constant value, bounded by first and second slopes ofdifferent signs, the method comprising:sensing the analog signal;detecting the first and second slopes independent of amplitude values;initiating a first binary output value only in response to detecting afirst slope, and maintaining that first binary output value in thepresence of a subsequent substantially constant amplitude value until asecond slope is detected; and initiating a second binary output value,only in response to detecting the second slope, and maintaining thatsecond binary output value in the presence of a subsequent substantiallyconstant amplitude value until a first slope is detected.
 18. A methodas in claim 17 including smoothing peak amplitudes of the analog signalto remove noise therein.
 19. A method as in claim 18 wherein thesmoothing step includes substituting non-noisy representations of peakamplitudes for noisy peak amplitudes of the analog signal.
 20. A methodof processing a binary information-carrying analog signal with noisecarrying peak amplitudes, and with information identifying slopestherebetween, the method comprising:sensing the analog signalsubstituting non-noisy peak amplitude values for the noise carrying peakamplitudes thereby forming a substantially noise-free representation ofthe analog signal with the noise-free representation including theinformation identifying slopes; and detecting the informationidentifying slopes in the representation, and only in response thereto,generating a binary output signal having only first and second valuesthat correspond to the binary information in the analog signal.